System and method for saturation detection, correction and recovery in a polar transmitter

ABSTRACT

A system for saturation detection, correction and recovery in a power amplifier includes a power amplifier, a closed power control loop configured to develop a power control signal (V PC ), and power control circuitry configured to reduce the power control signal if the power amplifier is operating in a saturation mode.

BACKGROUND

With the increasing availability of efficient, low cost electronicmodules, portable communication devices are becoming more and morewidespread. A portable communication device includes one or more poweramplifiers for amplifying the power of the signal to be transmitted fromthe portable communication device.

With the decreasing size of portable communication devices, powerefficiency is one of the most important design criteria. Reducing powerconsumption prolongs power source life and extends stand-by and talktime of the portable communication device. In a portable communicationdevice that uses a non-constant amplitude output (i.e., one thatmodulates and amplifies both a phase component and an amplitudecomponent), a linear power amplifier is typically used. The powercontrol can be open loop or closed loop. In one example of a closed looppower control system, the amplitude signal is used to provide powercontrol in the closed feedback loop.

In a system that uses closed loop amplitude power control, it ispossible to saturate the amplitude power control loop, and thereby drivethe power amplifier into a saturated condition. When operating insaturation mode, the power amplifier can no longer respond to anincrease in the power control signal. This condition is worsened underextreme supply voltage conditions, such as low available batteryvoltage, and/or extreme temperature conditions, and when the poweramplifier is presented with a mismatched load, caused by, for example,movement of the antenna, or if the antenna is presented to a reflectivesurface, such as a metallic surface.

When the power control loop is saturated, RF parameters, such as the RFoutput spectrum, become degraded. It is desirable to detect the onset ofpower amplifier saturation, and controllably bring the power amplifierout of saturation before the power control loop starts to ramp down.

SUMMARY

Embodiments of the invention include a system for saturation detection,correction and recovery including a power amplifier, a closed powercontrol loop configured to develop a power control signal (V_(PC)), andpower control circuitry configured to reduce the power control signal ifthe power amplifier is operating in a saturation mode.

Related methods of operation are also provided. Other systems, methods,features, and advantages of the invention will be or become apparent toone with skill in the art upon examination of the following figures anddetailed description. It is intended that all such additional systems,methods, features, and advantages be included within this description,be within the scope of the invention, and be protected by theaccompanying claims.

BRIEF DESCRIPTION OF THE FIGURES

The invention can be better understood with reference to the followingfigures. The components within the figures are not necessarily to scale,emphasis instead being placed upon clearly illustrating the principlesof the invention. Moreover, in the figures, like reference numeralsdesignate corresponding parts throughout the different views.

FIG. 1 is a block diagram illustrating a simplified portable transceiverincluding a power amplifier control element according to one embodimentof the invention.

FIG. 2 is a block diagram illustrating the upconverter, power amplifiercontrol element and a saturation detection, correction and recoveryelement in accordance with an embodiment of the invention.

FIG. 3 is a graphical representation of the power output of the poweramplifier during a typical output burst.

FIG. 4 is a graphical representation of a portion of the output burst ofFIG. 3, illustrating the operation of the system and method forsaturation detection, correction and recovery.

FIG. 5 is a flow chart illustrating the operation of an embodiment ofthe system and method for saturation detection, correction and recovery.

FIG. 6 is a flow chart illustrating the operation of an alternativeembodiment of the system and method for saturation detection, correctionand recovery.

DETAILED DESCRIPTION

Although described with particular reference to a portable transceiver,the system and method for saturation detection, correction and recoverycan be implemented in any communication device employing a closedfeedback power control loop. Furthermore, in some implementations, thesystem and method for saturation detection, correction and recovery canprevent the power amplifier from entering saturation or cause the poweramplifier to gracefully exit saturation as soon as even minimalsaturation is detected.

The system and method for saturation detection, correction and recoverycan be implemented in hardware, software, or a combination of hardwareand software. When implemented in hardware, the system and method forsaturation detection, correction and recovery can be implemented usingspecialized hardware elements and logic. When the system and method forsaturation detection, correction and recovery is implemented partiallyin software, the software portion can be used to control components inthe power amplifier control element so that various operating aspectscan be software-controlled. The software can be stored in a memory andexecuted by a suitable instruction execution system (microprocessor).The hardware implementation of the system and method for saturationdetection, correction and recovery can include any or a combination ofthe following technologies, which are all well known in the art:discrete electronic components, a discrete logic circuit(s) having logicgates for implementing logic functions upon data signals, an applicationspecific integrated circuit having appropriate logic gates, aprogrammable gate array(s) (PGA), a field programmable gate array(FPGA), etc.

The software for the system and method for saturation detection,correction and recovery comprises an ordered listing of executableinstructions for implementing logical functions, and can be embodied inany computer-readable medium for use by or in connection with aninstruction execution system, apparatus, or device, such as acomputer-based system, processor-containing system, or other system thatcan fetch the instructions from the instruction execution system,apparatus, or device and execute the instructions.

In the context of this document, a “computer-readable medium” can be anymeans that can contain, store, communicate, propagate, or transport theprogram for use by or in connection with the instruction executionsystem, apparatus, or device. The computer readable medium can be, forexample but not limited to, an electronic, magnetic, optical,electromagnetic, infrared, or semiconductor system, apparatus, device,or propagation medium. More specific examples (a non-exhaustive list) ofthe computer-readable medium would include the following: an electricalconnection (electronic) having one or more wires, a portable computerdiskette (magnetic), a random access memory (RAM), a read-only memory(ROM), an erasable programmable read-only memory (EPROM or Flash memory)(magnetic), an optical fiber (optical), and a portable compact discread-only memory (CDROM) (optical). Note that the computer-readablemedium could even be paper or another suitable medium upon which theprogram is printed, as the program can be electronically captured, viafor instance optical scanning of the paper or other medium, thencompiled, interpreted or otherwise processed in a suitable manner ifnecessary, and then stored in a computer memory.

FIG. 1 is a block diagram illustrating a simplified portable transceiver100 including an embodiment of a system and method for saturationdetection, correction and recovery. The portable transceiver 100includes speaker 102, display 104, keyboard 106, and microphone 108, allconnected to baseband subsystem 110. A power source 142, which may be adirect current (DC) battery or other power source, is also connected tothe baseband subsystem 110 via connection 144 to provide power to theportable transceiver 100. In a particular embodiment, portabletransceiver 100 can be, for example but not limited to, a portabletelecommunication device such as a mobile cellular-type telephone.Speaker 102 and display 104 receive signals from baseband subsystem 110via connections 112 and 114, respectively, as known to those skilled inthe art. Similarly, keyboard 106 and microphone 108 supply signals tobaseband subsystem 110 via connections 116 and 118, respectively.Baseband subsystem 110 includes microprocessor (μP) 120, memory 122,analog circuitry 124, and digital signal processor (DSP) 126 incommunication via bus 128. Bus 128, although shown as a single bus, maybe implemented using multiple busses connected as necessary among thesubsystems within baseband subsystem 110.

Depending on the manner in which the system and method for softsaturation detection and correction is implemented, the basebandsubsystem 110 may also include one or more of an application specificintegrated circuit (ASIC) 135 and a field programmable gate array (FPGA)133.

Microprocessor 120 and memory 122 provide the signal timing, processingand storage functions for portable transceiver 100. Analog circuitry 124provides the analog processing functions for the signals within basebandsubsystem 110. Baseband subsystem 110 provides control signals totransmitter 150, receiver 170 power amplifier 180 and the poweramplifier control element 285 such as through connection 132 forexample.

The baseband subsystem 110 generates a power control signal, referred toas V_(APC) which is supplied to the power amplifier control element 285via connection 146. The power control signal V_(APC) is generated by thebaseband subsystem 110 and is converted to an analog control signal bythe digital-to-analog converter (DAC) 138, which will be describedbelow. The power control signal V_(APC) is illustrated as being suppliedfrom the bus 128 to indicate that the signal may be generated indifferent ways as known to those skilled in the art. The power controlsignal V_(APC) is a reference voltage signal that defines the transmitpower level and provides the power profile. Generally, the power controlsignal, V_(APC), controls the power amplifier as a function of the peakvoltage of the power amplifier determined during calibration, andcorresponds to power amplifier output power.

The control signals on connections 132 and 146 may originate from theDSP 126, the ASIC 135, the FPGA 133, or from microprocessor 120, and aresupplied to a variety of connections within the transmitter 150,receiver 170, power amplifier 180, and the power amplifier controlelement 285. It should be noted that, for simplicity, only the basiccomponents of the portable transceiver 100 are illustrated herein. Thecontrol signals provided by the baseband subsystem 110 control thevarious components within the portable transceiver 100. Further, thefunction of the transmitter 150 and the receiver 170 may be integratedinto a transceiver.

As will be discussed below, the power amplifier control element 285generates a power amplifier (PA) power control voltage, referred to asV_(PC). The PA power control voltage, V_(PC), controls the power outputof the power amplifier 180 based on an amplitude reference signal. ThePA power control voltage, V_(PC), is generated in a closed power controlloop that is formed by the components in the power amplifier controlelement 285, which will be described below. In an embodiment inaccordance with the invention, the PA power control voltage, V_(PC), isalso supplied to the baseband subsystem 110. In accordance with anembodiment, the baseband subsystem 110 contains components (not shown inFIG. 1) that compare the magnitude of the V_(PC) signal against areference signal, V_(REF). The reference signal, V_(REF), establishes athreshold. As will be described below, when the PA power controlvoltage, V_(PC), exceeds the level of the reference signal, V_(REF), thepower amplifier is said to be in saturation. After saturation of thepower amplifier 180 is detected, the baseband subsystem 110 reacts bycontrollably adjusting the level of the power control signal, V_(APC),by reducing the gain control voltage supplied to amplifiers in the powercontrol element 285. In this manner, the power amplifier is controllablybacked out of saturation.

If portions of the system and method for saturation detection,correction and recovery are implemented in software that is executed bythe microprocessor 120, the memory 122 will also include saturationdetection, correction and recovery software 255. The saturationdetection, correction and recovery software 255 comprises one or moreexecutable code segments that can be stored in the memory and executedin the microprocessor 120. Alternatively, the functionality of thesaturation detection, correction and recovery software 255 can be codedinto the ASIC 135 or can be executed by the FPGA 133, or another device.Because the memory 122 can be rewritable and because the FPGA 133 isreprogrammable, updates to the saturation detection, correction andrecovery software 255 can be remotely sent to and saved in the portabletransceiver 100 when implemented using either of these methodologies.

Baseband subsystem 110 also includes analog-to-digital converter (ADC)134 and digital-to-analog converters (DACs) 136 and 138. In thisexample, the DAC 136 generates the in-phase (I) and quadrature-phase (Q)signals 140 that are applied to the modulator 152. The DAC 138 generatesthe ramp up/power control signal, V_(APC), on connection 146. ADC 134,DAC 136 and DAC 138 also communicate with microprocessor 120, memory122, analog circuitry 124 and DSP 126 via bus 128. DAC 136 converts thedigital communication information within baseband subsystem 110 into ananalog signal for transmission to a modulator 152 via connection 140.Connection 140, while shown as two directed arrows, includes theinformation that is to be transmitted by the transmitter 150 afterconversion from the digital domain to the analog domain.

The transmitter 150 includes modulator 152, which modulates the analoginformation on connection 140 and provides a modulated signal viaconnection 158 to upconverter 154. The upconverter 154 transforms themodulated signal on connection 158 to an appropriate transmit frequencyand provides the upconverted signal to a power amplifier 180 viaconnection 184. The power amplifier 180 amplifies the signal to anappropriate power level for the system in which the portable transceiver100 is designed to operate.

Details of the modulator 152 and the upconverter 154 have been omitted,as they will be understood by those skilled in the art. For example, thedata on connection 140 is generally formatted by the baseband subsystem110 into in-phase (I) and quadrature (Q) components. The I and Qcomponents may take different forms and be formatted differentlydepending upon the communication standard being employed. For example,when the power amplifier module is used in a constant-amplitude, phase(or frequency) modulation application such as the global system formobile communications (GSM), the phase modulated information is providedby the modulator 152. When the power amplifier module is used in anapplication requiring both phase and amplitude modulation such as, forexample, extended data rates for GSM evolution, referred to as EDGE, theCartesian in-phase (I) and quadrature (Q) components of the transmitsignal are converted to their polar counterparts, amplitude and phase.The phase modulation is performed by the modulator 152, while theamplitude modulation is performed by the power amplifier control element285, where the amplitude envelope is defined by the PA power controlvoltage V_(PC), which is generated by the power amplifier controlelement 285.

The instantaneous power level of the power amplifier module 180 tracksV_(PC), thus generating a transmit signal with both phase and amplitudecomponents. This technique, known as polar modulation, eliminates theneed for linear amplification by the power amplifier module, allowingthe use of a more efficient saturated mode of operation while providingboth phase and amplitude modulation.

The power amplifier 180 supplies the amplified signal via connection 156to a front end module 162. The front end module comprises an antennasystem interface that may include, for example, a diplexer having afilter pair that allows simultaneous passage of both transmit signalsand receive signals, as known to those having ordinary skill in the art.The transmit signal is supplied from the front end module 162 to theantenna 160.

Using the PA power control voltage, V_(PC), generated by the poweramplifier control element 285, the power amplifier control element 285determines the appropriate power level at which the power amplifier 180operates to amplify the transmit signal. The PA power control voltage,V_(PC), is also used to provide envelope, or amplitude, modulation whenrequired by the modulation standard. The power amplifier control element285 will be described in greater detail below.

A signal received by antenna 160 will be directed from the front endmodule 162 to the receiver 170. The receiver 170 includes adownconverter 172, a filter 182, and a demodulator 178. If implementedusing a direct conversion receiver (DCR), the downconverter 172 convertsthe received signal from an RF level to a baseband level (DC), or anear-baseband level (˜100 kHz). Alternatively, the received RF signalmay be downconverted to an intermediate frequency (IF) signal, dependingon the application. The downconverted signal is sent to the filter 182via connection 174. The filter comprises a least one filter stage tofilter the received downconverted signal as known in the art.

The filtered signal is sent from the filter 182 via connection 176 tothe demodulator 178. The demodulator 178 recovers the transmitted analoginformation and supplies a signal representing this information viaconnection 186 to ADC 134. ADC 134 converts these analog signals to adigital signal at baseband frequency and transfers the signal via bus128 to DSP 126 for further processing.

FIG. 2 is a block diagram illustrating the upconverter 154, poweramplifier control element 285 and a saturation detection and powercontrol element 300 in accordance with an embodiment of the invention.Beginning with a description of the power amplifier control element 285,which forms a closed power control loop 265, also referred to as an “AMcontrol loop,” a portion of the output power present at the output ofpower amplifier 180 on connection 156 is diverted by coupler 222 viaconnection 157 and input to a mixer 226. The mixer 226 also receives alocal oscillator (LO) signal from a synthesizer 148 via connection 198.

The mixer 226 downconverts the RF signal on connection 157 to anintermediate frequency (IF) signal on connection 228. For example, themixer 226 takes a signal having a frequency of approximately 2 gigahertz(GHz) on connection 157 and downconverts it to a frequency ofapproximately 100 megahertz (MHz) on connection 228 for input tovariable gain element 232. The variable gain element 232 can be, forexample but not limited to, a variable gain amplifier or an attenuator.In such an arrangement, the variable gain element 232 might have adynamic range of approximately 70 decibels (dB) i.e., +35 dB/−35 dB. Thevariable gain element 232 receives a control signal input from thenon-inverting output of an adder 330 via connection 234. The adderreceives the power control signal, V_(APC), from an amplifier 236. Theinput to amplifier 236 is the power control signal, V_(APC), which issupplied via connection 146 from the baseband subsystem 110 of FIG. 1.The V_(APC) signal on connection 146 is a reference voltage signal thatdefines the transmit power level and provides the power profile. Thesignal on connection 146 is supplied to a reconstruction filter, whichincludes resistor 240 and capacitor 242. In this manner, a referencevoltage for the transmit power level and power profile is supplied viaconnection 234 to the control input of the variable gain element 232.

The output of the variable gain element 232 on connection 246 is an IFsignal and includes modulation having both an AM component and a PMcomponent and is called a “power measurement signal.” This powermeasurement signal is related to the absolute output power of poweramplifier 180, and includes a very small error related to the AM and PMcomponents present in the signal. The output of the variable gainelement 232 on connection 246 is supplied to the input of power detector262 and is also supplied to a limiter 248. The IF signal on connection246 includes both an AM component and a PM component. The signal onconnection 246 is supplied to a power detector 262, which provides, onconnection 264, a baseband signal representing the instantaneous levelof intermediate frequency (IF) power present on connection 246. Theoutput of the power detector 262 on connection 264 is supplied to theinverting input of amplifier 268.

The amplifier 268, the capacitor 266 and the capacitor 270 form acomparator 284, which provides the error signal used to control thepower amplifier 180 via connection 272. The non-inverting input to theamplifier 268 is supplied via connection 139 from the output of themodulator 152 through the power detector 276. The signal on connection139 is supplied to the non-inverting input of the amplifier 268 andcontains the AM modulation developed by the modulator 152 for input tothe control port 168 of the power amplifier 180.

The gain of the power amplifier control element 285 amplifies the signalon connection 272 such that the difference between the signals onconnection 264 and on connection 139 input to amplifier 268 provide anerror signal on connection 272 that is used to control the output of thepower amplifier 180. The error signal on connection 272 is supplied tovariable gain element 274, which can be similar in structure to thevariable gain element 232. However, the variable gain element 274 has afunction that is inverse to the function of the variable gain element232. The control input to variable gain element 274 is supplied from theinverting output of the adder 330 via connection 230. In this manner,the PA power control voltage, V_(PC), supplied to the control port 168of the power amplifier 180 drives the power amplifier 180 to provide theproper output on connection 156.

The level of the signal on connection 264 and the level of the signal onconnection 139 should be equal. For example, if the output level of thevariable gain element 232 is increased by a factor of 10, then the levelof the output of power amplifier 180 should be decreased accordingly, tomaintain equilibrium at the input of the amplifier 268. The output ofthe power amplifier 180 changes to cancel the gain change of variablegain element 232. In this manner, the amplitude of the signal onconnection 264 remains equal to the amplitude of the signal onconnection 139. However, this implies that the signal on connection 228lags the signal on connection 234 with the result that the two signalswill not completely cancel. In this manner, an error signal with an AMportion and a PM portion is present on connection 246. The signal onconnection 246 is converted by power detector 262 from an IF signal to abaseband signal on connection 264. The signal on connection 264 isamplified by variable gain element 268 and variable gain element 274 andprovided as input to the power amplifier control port on connection 168.The power amplifier control element 285 has sufficient gain so that theerror signal on connection 264 can be kept small. In such a case, thegain changes of variable gain element 232 and the power amplifier 180will substantially be the inverse of each other.

In addition to amplifying the error signal on connection 264, thevariable gain element 268 also compares the power measurement signal onconnection 264 with a reference voltage signal including an AM portionon connection 139, supplied by the modulator 152. The DC voltage levelon connection 139 affects the desired static output power for the poweramplifier 268, irrespective of AM modulation. The amplifier 268 comparesthe signal level on connection 264 with the signal level on connection139 and then amplifies the difference, thus providing a power controlsignal on connection 272. The comparator 284 functions as an integrator,which is also a low pass filter. Alternatively, the AM portion of thesignal may be introduced to the power amplifier control element 285 inother ways, such as, for example, through the variable gain element 232.

The power control signal on connection 272 drives the variable gainelement 274, which corrects for the effect that the variable gainelement 232 has on the transfer function of the power amplifier controlelement 285. The variable gains of the variable gain element 232 andvariable gain element 274 are complimentary. Because the powermeasurement signal is present on connection 264 and the AM error signalis present on connection 139, the amplifier 268 provides a dualfunction; (1) it amplifies the AM error signal on connection 139 so asto modulate the power output of power amplifier 180 via connection 250to have the correct amount of AM; and (2) it performs the average powercomparison and amplifies the result, thus providing a control signal onconnection 272 that drives the variable gain element 274. The variablegain element 274 provides the PA power control voltage, V_(PC), onconnection 168, which includes the AM portion and which controls theoutput of the power amplifier 180. In this manner, power output iscontrolled and the desired AM portion of the signal is supplied to thecontrol input 168 (V_(PC)) of power amplifier 180 and made present onthe power amplifier output on connection 156. The mixer 226, variablegain element 232, power detector 262, amplifier 268 and the variablegain element 274 provide a continuous closed power control loop 265 tocontrol the power output of power amplifier 180, while allowing for theintroduction of the AM portion of the transmit signal via connection139.

In accordance with an embodiment of the invention, the PA power controlvoltage, V_(PC), is also supplied to a saturation detection, correctionand recovery element 300, which can be located in the RF section. Inaccordance with an embodiment, the PA power control voltage, V_(PC), issupplied via connection 168 to the non-inverting input of a comparator310. The comparator 310 can be, for example, a differential comparator.A reference voltage signal, V_(REF) is formed at the node 306 byresistors 302 and 304 using the input voltage signal, V_(CC), as input.The value of V_(CC) depends on the system voltage level and the value ofthe resistors 302 and 304 is chosen based on system operatingparameters. The reference voltage, V_(REF), can be created from a bandgap voltage that is supply-independent, as known in the art. Thereference voltage signal, V_(REF), is supplied via connection 306 to theinverting input of the comparator 310. The reference voltage signal,V_(REF), is used as a threshold against which to measure the level ofthe PA power control voltage, V_(PC).

When the power amplifier 180 approaches saturation, its power controlgain decreases. This means that to achieve the same proportion in outputpower per change in the level of the PA power control voltage, V_(PC),the V_(PC) signal must increase much more compared to when the poweramplifier was not in saturation. When the power amplifier is close tosaturation, the closed power control loop 265 increases the level of theV_(PC) signal in order to increase the power amplifier output power. Ifthe power amplifier does not reach the required power level, then theclosed power control loop 265 increases V_(PC) as high as possible.Therefore, when the V_(PC) signal is at its maximum based on supplyvoltage, it is an indication that the power amplifier is approachingsaturation. The reference voltage, V_(REF), on connection 305 isselected to be higher than the maximum voltage of V_(PC), which wouldgive the highest power level from the power amplifier without the poweramplifier entering saturation.

The comparator 310 continuously compares the level of the PA powercontrol voltage, V_(PC), against the reference voltage signal, V_(REF).When the level of the PA power control voltage, V_(PC), exceeds thelevel of the reference voltage signal, V_(REF), the output of thecomparator 310 goes to a logic high state, which closes a switch 314 andcauses a current source 312 to turn on. The current source 312 begins tocharge a capacitor 318. As long as the output of the comparator 310remains logic high, the current source 312 charges the capacitor 318.

A transistor 322 is coupled in parallel with the capacitor 318. Thetransistor 322 is controlled by a transmit enable (TX_(EN)) signalsupplied from the baseband subsystem 110 via connection 332. The TX_(EN)signal is supplied to an optional OR gate 348, which will be describedbelow, and then to an amplifier 336. The output of the amplifier 336 onconnection 338 is coupled to the gate of the transistor 322. Whileillustrated as a field effect transistor, the transistor 322 may beimplemented using other technologies.

The signal on connection 316 is supplied to a scaling buffer 324 andthen to the adder 330 via connection 326. The signal on connection 326is subtracted from the output of the amplifier 236, thus reducing thelevel of the control signal supplied to the variable gain element 232and the variable gain element 274. This reduction in control voltagedynamically forces the power control element 285 to lower the targetoutput power of the power amplifier (or suspend any increase in power),thus preventing the power amplifier 180 from going deeper intosaturation, and eventually exiting saturation. When the output of thecomparator 310 goes to logic low, indicating that the level of thereference voltage signal V_(REF), is higher than the PA power controlvoltage, V_(PC), the switch 314 opens, thus suspending the charging ofthe capacitor 318. The capacitor 318 maintains its charge, and the powercontrol loop 265 therefore preserves its power of operation just belowsaturation, until the TX_(EN) signal goes to logic low. The transitionof the TX_(EN) signal to logic low signals the end of the transmitburst. At this time the capacitor 318 is discharged and awaits the nexttransmit burst.

In an alternative and optional application, the saturation detection,correction and recovery element 300 includes another comparator 320. Thecomparator 320 can be similar to the comparator 310. The PA powercontrol signal, V_(PC), is supplied to the inverting input of thecomparator 320. A second reference voltage signal, V_(REF2), isdeveloped using the resistors 342 and 344 at node 352. The secondreference voltage signal, V_(REF2), is smaller in magnitude than thefirst reference voltage signal V_(REF), and is supplied to thenon-inverting input of the comparator 320. When the output of thecomparator 320 goes to logic high, indicating that the level of thereference voltage signal V_(REF2) is higher than the PA power controlvoltage, V_(PC), the logic high output of the comparator 320 onconnection 346 is sent to the OR-gate along with the TX_(EN) signal onconnection 332, thus causing the output of the OR gate 348 to transitionto logic high and thus discharge the capacitor 318. Either the TX_(EN)signal or the drop of V_(PC) below V_(REF2) can reset the capacitance.

In this manner, the power amplifier 180 can be controllably preventedfrom going into saturation or if in saturation, backed out of saturationsoftly without violating switching transient requirements in the GSMcommunication standard.

The circuitry in the saturation detection, correction and recoveryelement 300 other than the comparator 310 (and the comparator 320 ifimplemented) may be activated only when saturation is detected. In thismanner, the impact of this circuitry on the transmitter output power islimited to a few dB and will not degrade system performance. Thesaturation detection, correction and recovery element 300 contributes toimproving the robustness of the transmitter 150 with respect to supplyvoltage variation and voltage standing wave ratio (VSWR) due to loadvariations.

At all times, the closed power control loop 265 allows the correction ofany phase shift caused by power amplifier 180. The phase locked loop 220includes a closed power control feedback loop for looping back theoutput of power amplifier 180 to the input of phase/frequency detector208. Any unwanted phase shift generated by the power amplifier 180 willbe corrected by the phase locked loop 220. The output of variable gainelement 232 passes any phase distortion present via connection 246 tolimiter 248 for correction by the phase locked loop 220. As such, thephase of the output of power amplifier 180 is forced to follow the phaseof the LO signal on connection 155.

To remove the AM from the output of variable gain element 232, thevariable gain element 232 is connected via connection 246 and connection144 to the input of limiter 248. The limiter 248 develops a localoscillator signal containing only a PM component on connection 258. ThisLO signal is supplied via connection 258 to a divider 260, which dividesthe signal on connection 258 by a number, “y.” The number “y” is chosenso as to minimize the design complexity of the synthesizer 148. Theoutput of the divider 260 is supplied to the phase/frequency detector208.

An unmodulated input signal from synthesizer 148 is supplied to thedivider 202 via connection 155. The unmodulated input signal isfrequency divided by a number “x” to provide a signal having anappropriate frequency on connection 204. The number “x” is chosen tominimize the design complexity of the synthesizer 148 and can be, forexample, but not limited to, chosen to convert the output of thesynthesizer 148 to a frequency of 100 MHz. The output of the divider onconnection 204 is supplied to the modulator 152. In addition, thebaseband I and Q information signals are supplied via connections 278and 282, respectively, to the modulator 152. The I and Q basebandinformation signal interface is understood by those having ordinaryskill in the art. As a result of the operation of the modulator 152, theoutput on connection 252 is an intermediate frequency signal includingan AM component in the form of an AM reference signal and a small PMerror signal. The output of modulator 152 is supplied via connection 252to power detector 276. The output of power detector 276 also includesthe AM portion of the desired transmit signal. The signal provided onconnection 139 is a reference signal for input to the power amplifiercontrol element 285. Because the power amplifier control element 285 haslimited bandwidth, the rate at which the amplitude modulation occurs onconnection 139 is preferably within the bandwidth of the power controlfeedback loop 265.

The components within the phase locked loop 220 provide gain for thecomparison of the PM on connection 258 and the modulator connections 278and 282, thus providing a phase error output of the modulator 152 onconnection 252. This phase error signal is then supplied to limiter 248,which outputs a signal on connection 258 containing the small PM phaseerror component.

The error signal output of modulator 152 on connection 252 containingthe phase error, will get smaller and smaller as the gain of the phaselocked loop 220 increases. However, there will always be some errorsignal present, thus enabling the phase locked loop 220 to achieve phaselock. It should be noted that even when the power amplifier 180 is notoperating, there will always be some small leakage through the poweramplifier 180 onto connection 156. This small leakage is sufficient toprovide a feedback signal through the variable gain element 232 and intothe phase locked loop 220 such that the phase locked loop 220 can belocked using just the leakage output of power amplifier 180. In thismanner, a single feedback loop can be used to continuously control theoutput power of power amplifier 180 from the time that the amplifier isoff through the time when the amplifier 180 is providing full outputpower.

The output of the modulator 152 is supplied via connection 252 to alimiter 249. The limiter 249 cancels the AM component present onconnection 252, thereby preventing any AM-to-PM conversion in thephase/frequency detector 208. The phase/frequency detector 208 receivesan unmodulated input signal from the limiter 249. The phase/frequencydetector 208 also receives the output of divider 260 via connection 206.The phase/frequency detector 208 detects any phase difference betweenthe signal on connection 256 and the signal on connection 206 and placesa signal on connection 210 that has an amplitude proportional to thedifference. When the phase difference reaches 360°, the output ofphase/frequency detector 208 on connection 210 will become proportionalto the frequency difference between the signals on connections 256 and206.

The output of phase/frequency detector 208 on connection 210 is adigital signal having a value of either a 0 or a 1 with a very smalltransition time between the two output states. This signal on connection210 is supplied to low-pass filter 212, which integrates the signal onconnection 210 and places a DC signal on connection 214 that controlsthe frequency of the transmit voltage control oscillator (TX VCO) 216.The output of TX VCO 216 is supplied via connection 184 directly to thepower amplifier 180. In this manner, the synthesizer 148, limiter 248,modulator 152, limiter 256, divider 260, divider 202, phase/frequencydetector 208, low-pass filter 212 and TX VCO 216 form a phase lockedloop (PLL) 220, which is used to determine the transmit frequency onconnection 184. Alternatively, the modulator 152 may reside outside ofthe PLL 220.

When the PLL 220 is settled, or “locked,” then the two signals enteringthe phase/frequency detector 208 on connections 256 and 206 havesubstantially the same phase and frequency, and the output of thephase/frequency detector 208 on connection 210 goes to zero. The outputof the integrating low-pass filter 212 on connection 214 stabilizes,resulting in a fixed frequency out of TX VCO 216. For example, thesynthesizer 148 and the mixer 226 ensure that the frequency of thesignal output from the TX VCO 216 on connection 184 tracks the sum ofthe frequencies of the local oscillator signal supplied by synthesizer148 and the IF frequency on connection 206.

When the phase locked loop 220 is locked, the phase of the signal onconnection 256 and the phase of the signal on connection 206 will besubstantially equal. Because the amount of PM on connection 206 shouldbe very small, the gain in the phase locked loop 220 has to besufficiently high to amplify the error signal on connection 206 to alevel at which the phase/frequency detector 208 can make a comparison.By using the modulator 152 to impose the I and Q information signals onthe signal on connection 204 in a direction opposite from which it isdesirable for the phase of the TX VCO to move, and because it isdesirable for the phase locked loop 220 to remain locked, the phase ofthe signal output from the TX VCO 216 on connection 184 will moveopposite that of the phase imposed by the modulator 152. In this manner,the PM error signal present on connection 206 is minimized by the veryhigh sensitivity, of the order of many MHz per volt, of the TX VCO 216.

Because the power amplifier control element 285 is a closed loop for AMsignals at connection 139, it is possible to use a non-linear, andtherefore highly efficient, power amplifier 180. Furthermore, theundesirable and detrimental AM-to-PM conversion, which occurs due to theamplitude dependence of an amplifier's phase shift, is rectified by thepower amplifier 180 being included within the phase locked loop 220. Byseparating the AM and the PM modulation and by providing closed loopcontrol for both the AM and PM modulation, a non-linear, and thereforehighly efficient power amplifier can be used. The power amplifiercontrol element 285 provides the AM portion of the signal and controlsthe output of the power amplifier 180 in such a way as to minimize lowpower inefficiency.

FIG. 3 is a graphical representation of the power output of the poweramplifier during a typical output burst 400. The curve 410 illustratesthe desired power output of the power amplifier 180. A power versus timemask 402 defines the power and time parameters within which the curve410 must remain to comply with regulatory requirements. As shown in FIG.3, the curve 410 indicates that output power remains below −70 dB untilthe beginning of the burst 400. In this example, the burst time is156.25 bits, which corresponds to 577 μs and is indicated usingreference numeral 416. The portion of the burst in which data istransmitted is 148 bits in duration, which corresponds to 542.8 μs, andis indicated using reference numeral 418. The ramp up of the curve 410occurs in the 18 μs preceding the beginning of the period 418 and theramp down of the curve 410 occurs in the 18 μs after the period 418. Thecurve 412, indicated with a doted line, indicates a deeply saturatedpower amplifier and the curve 414, also indicated with a dotted line,indicates a minimally saturated power amplifier. The curves 412 and 414illustrate two exemplary saturation conditions of the power amplifier180 (FIG. 2). In accordance with an embodiment of the invention, thesaturation condition is detected and compensated, as described above.

FIG. 4 is a graphical representation of a portion 450 of the outputburst of FIG. 3, illustrating the operation of the system and method forsaturation detection, correction and recovery. The power versus timemask 402 is shown for reference. The curve 414 represents the output ofa minimally saturated power amplifier. The point 422 is the point atwhich saturation of the power amplifier 180 is detected, as describedabove. In accordance with an embodiment of the invention, at the point422 when saturation is detected, the output of the comparator 310 (FIG.2) transitions to logic high. In an embodiment, this is accomplished bycomparing the PA power control voltage, V_(PC), to the reference voltagesignal, V_(REF). When the level of the power control voltage, V_(PC),exceeds the level of the reference voltage signal, V_(REF), thecomparator 310 sends an indicator signal on connection 308 closing theswitch 314 (FIG. 2), which initiates the charging of the capacitor 318(FIG. 2). The closing of the switch 314 (FIG. 2) is indicated at 420 inFIG. 4.

As the capacitor charges during the time period Δt, the signal onconnection 316 (FIG. 2) is supplied to a scaling buffer 324 (FIG. 2) andthen to the adder 330 (FIG. 2) via connection 326. The signal onconnection 326 is subtracted from the output of the amplifier 236, thusreducing the level of the control signal supplied to the variable gainelement 232 and the variable gain element 274 (FIG. 2). This reductionin control voltage dynamically forces the power control element 285 tolower the target output power of the power amplifier (or suspend anyincrease in power), thus preventing the power amplifier 180 from goinginto saturation, or, if already in saturation, causing the poweramplifier to exit saturation, as indicated at point 425. When the outputof the comparator 310 goes to logic low, indicating that the level ofthe reference voltage signal V_(REF), is higher than the PA powercontrol voltage, V_(PC), the switch 314 opens, thus suspending thecharging of the capacitor 318. The capacitor 318 retains its charge, asindicated at 427, and the power control loop 265 therefore preserves itspower of operation just below saturation, until the TX_(EN) signal goesto logic low. The level of the PA power control voltage, V_(PC), iscontinuously compared against the reference voltage signal, V_(REF), bythe comparator 310 (FIG. 2).

FIG. 5 is a flow chart illustrating the operation of an embodiment ofthe system and method for saturation detection, correction and recovery.The blocks in the flowchart can be performed in the order shown, out ofthe order shown, or can be performed in parallel. In block 502, thelevel of the PA power control voltage, V_(PC), is measured. In block504, the level of the PA power control voltage, V_(PC), is comparedagainst the level of the reference voltage level, V_(REF). If the levelof the PA power control voltage, V_(PC), is equal to or lower than thelevel of the reference voltage level, V_(REF), the process returns toblock 502. If the level of the PA power control voltage, V_(PC), exceedsthe level of the reference voltage level, V_(REF), then, in block 506,the output of the comparator 310 (FIG. 2) goes to a logic high state,which closes the switch 314 and causes the current source 312 to turnon. The current source 312 begins to charge a capacitor 318. As long asthe output of the comparator 310 remains logic high, the current source312 charges the capacitor 318.

In block 508, the signal on connection 316 is supplied to a scalingbuffer 324 and then to the adder 330 via connection 326. The signal onconnection 326 is subtracted from the output of the amplifier 236, thusreducing the level of the control signal supplied to the variable gainelement 232 and the variable gain element 274. As a result of thereduction in control voltage, the power control element 285 lowers thetarget output power of the power amplifier (or suspend any increase inpower), thus causing the power amplifier to exit saturation.

In block 512, the level of the PA power control voltage, V_(PC), iscompared against the level of the reference voltage level, V_(REF). Ifthe level of the PA power control voltage, V_(PC), is greater than thereference voltage level, V_(REF), then the process returns to block 506and the capacitor continues charging. If the level of the PA powercontrol voltage, V_(PC), is equal to or lower than the level of thereference voltage level, V_(REF), then, in block 514, the output of thecomparator 310 (FIG. 2) goes to a logic low state, which opens theswitch 314 and causes the current source 312 to turn off and cause thecapacitor 318 to stop charging. The capacitor 318 maintains its charge,and the power control loop 265 therefore preserves its power ofoperation just below saturation, until the TX_(EN) signal goes to logiclow.

FIG. 6 is a flow chart illustrating the operation of an alternativeembodiment of the system and method for saturation detection, correctionand recovery. In block 602 it is determined if the signal TX_(EN) islogic low. If TX_(EN) is logic low, then in block 604, the capacitor 318is discharged using the amplifier 336 (FIG. 2). If it is determined inblock 602 that TX_(EN) is logic high, then in block 606 it is determinedif the PA power control voltage, V_(PC) is less than the value of thevoltage reference signal, V_(REF2). If the PA power control voltage,V_(PC) is less than the value of the voltage reference signal, V_(REF2),then in block 608, the capacitor 318 is discharged using the amplifier336 (FIG. 2). If the PA power control voltage, V_(PC) is not less thanthe value of the voltage reference signal, V_(REF2), then the processends and the capacitor retains charge.

While various embodiments of the invention have been described, it willbe apparent to those of ordinary skill in the art that many moreembodiments and implementations are possible that are within the scopeof this invention. Accordingly, the invention is not to be restrictedexcept in light of the attached claims and their equivalents.

1. A method for saturation detection, correction and recovery in a poweramplifier, comprising: providing a radio frequency (RF) signal to apower amplifier; generating a power control signal (V_(PC)) in a closedpower control loop; providing the power control signal to a comparator;comparing the power control signal to a reference signal; determiningfrom the comparison whether the power amplifier is operating in asaturation mode; and if the power amplifier is operating in a saturationmode reducing the power control signal to the power amplifier.
 2. Themethod of claim 1, wherein reducing the power control signal to thepower amplifier further comprises reducing a control signal to avariable gain element in the closed power control loop.
 3. The method ofclaim 2, in which the control signal is reduced by circuitry thatreduces the current supplied to the control signal of the variable gainelement.
 4. The method of claim 3, in which the reference signal isprogrammable.
 5. The method of claim 3, in which the circuitry comprisesa current source and a capacitance.
 6. The method of claim 5, in whichthe capacitance maintains charge throughout a transmit burst.
 7. Themethod of claim 1, further comprising reducing the power control signal(V_(PC)) to maintain an output power of the power amplifier just belowsaturation.
 8. A system for saturation detection, correction andrecovery in a power amplifier, comprising: a power amplifier; a closedpower control loop configured to develop a power control signal(V_(PC)); and power control circuitry configured to reduce the powercontrol signal if the power amplifier is operating in a saturation mode,wherein the power control circuitry further comprises: a comparatorconfigured to receive the power control signal and a reference signaland develop a logic high signal if the power control signal exceeds thereference signal; a switch, a current source and a capacitance at theoutput of the comparator, the switch configured to close when the outputof the comparator is logic high, the current source configured to chargethe capacitance when the switch is closed; and wherein the currentsupplied from the current source is subtracted from the power controlsignal.
 9. The system of claim 8, in which the reference signal isprogrammable.
 10. The system of claim 8, in which the capacitancemaintains charge throughout a transmit burst.
 11. The system of claim 8,further comprising an additional comparator configured to discharge thecapacitance prior to an end of a transmit burst.
 12. The system of claim8, in which the power control signal (V_(PC)) is reduced to maintain anoutput power of the power amplifier just below saturation.
 13. Thesystem of claim 8, in which the current source charges the capacitanceuntil the power amplifier exits saturation.